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Advance Information Enhanced Mixed Frequency Mode GreenLineTM PWM Controller:
Fixed Frequency, Variable Frequency, Standby Mode
The MC44603A is an enhanced high performance controller that is specifically designed for off-line and dc-to-dc converter applications. This device has the unique ability of automatically changing operating modes if the converter output is overloaded, unloaded, or shorted, offering the designer additional protection for increased system reliability. The MC44603A has several distinguishing features when compared to conventional SMPS controllers. These features consist of a foldback facility for overload protection, a standby mode when the converter output is slightly loaded, a demagnetization detection for reduced switching stresses on transistor and diodes, and a high current totem pole output ideally suited for driving a power MOSFET. It can also be used for driving a bipolar transistor in low power converters (< 150 W). It is optimized to operate in discontinuous mode but can also operate in continuous mode. Its advanced design allows use in current mode or voltage mode control applications. Current or Voltage Mode Controller * Operation up to 250 kHz Output Switching Frequency
MC44603A
MIXED FREQUENCY MODE GREENLINE PWM* CONTROLLER:
VARIABLE FREQUENCY, FIXED FREQUENCY, STANDBY MODE
* PWM = Pulse Width Modulation
16 1
P SUFFIX PLASTIC PACKAGE CASE 648
* * * * * * * * * * * * * * * * *
Inherent Feed Forward Compensation Latching PWM for Cycle-by-Cycle Current Limiting Oscillator with Precise Frequency Control
16 1
High Flexibility * Externally Programmable Reference Current Secondary or Primary Sensing Synchronization Facility High Current Totem Pole Output Undervoltage Lockout with Hysteresis
DW SUFFIX PLASTIC PACKAGE CASE 751G (SOP-16L)
PIN CONNECTIONS
VCC VC Output Gnd Foldback Input Overvoltage Protection (OVP) Current Sense Input Demag Detection 1 2 3 4 5 6 7 8 16 Rref R 15 Frequency Standby Voltage Feedback 14 Input 13 Error Amp Output 12 RPower Standby Soft-Start/Dmax/ 11 Voltage Mode 10 CT 9 Sync Input
Safety/Protection Features * Overvoltage Protection Against Open Current and Open Voltage Loop Protection Against Short Circuit on Oscillator Pin Fully Programmable Foldback Soft-Start Feature Accurate Maximum Duty Cycle Setting Demagnetization (Zero Current Detection) Protection Internally Trimmed Reference Enhanced Output Drive
GreenLine Controller: Low Power Consumption in Standby Mode * Low Startup and Operating Current Fully Programmable Standby Mode Controlled Frequency Reduction in Standby Mode Low dV/dT for Low EMI Radiations
Device GreenLine is a trademark of Motorola, Inc. MC44603AP MC44603ADW
This document contains information on a new product. Specifications and information herein are subject to change without notice.
(Top View)
ORDERING INFORMATION
Operating Temperature Range TA = -25 to +85C Package Plastic DIP-16 SOP-16L
Rev 0
(c) Motorola, Inc. 1997
MOTOROLA ANALOG IC DEVICE DATA
1
MC44603A
MAXIMUM RATINGS
Rating Total Power Supply and Zener Current Supply Voltage with Respect to Ground (Pin 4) Output Current (Note 1) Source Sink Output Energy (Capacitive Load per Cycle) RF Stby, CT, Soft-Start, Rref, RP Stby Inputs Foldback Input, Current Sense Input, E/A Output, Voltage Feedback Input, Overvoltage Protection, Synchronization Input Synchronization Input High State Voltage Low State Reverse Current Demagnetization Detection Input Current Source Sink Error Amplifier Output Sink Current Power Dissipation and Thermal Characteristics P Suffix, Dual-In-Line, Case 648 Maximum Power Dissipation at TA = 85C Thermal Resistance, Junction-to-Air DW Suffix, Surface Mount, Case 751G Maximum Power Dissipation at TA = 85C Thermal Resistance, Junction-to-Air Operating Junction Temperature Operating Ambient Temperature Symbol (ICC + IZ) VC VCC IO(Source) IO(Sink) W Vin Vin -0.3 to VCC + 0.3 VIH VIL Idemag-ib (Source) Idemag-ib (Sink) IE/A (Sink) VCC + 0.3 -20 -4.0 10 20 mA V mA mA Value 30 18 Unit mA V mA -750 750 5.0 -0.3 to 5.5 J V V
PD RJA PD RJA TJ TA
0.6 100 0.45 145 150 -25 to +85
W C/W W C/W C C
NOTES: 1. Maximum package power dissipation limits must be observed. 2. ESD data available upon request.
ELECTRICAL CHARACTERISTICS (VCC and VC = 12 V, [Note 3], Rref = 10 k, CT = 820 pF, for typical values TA = 25C,
for min/max values TA = -25 to +85C [Note 4], unless otherwise noted.) Characteristic OUTPUT SECTION Output Voltage (Note 5) Low State (ISink = 100 mA) Low State (ISink = 500 mA) High State (ISource = 200 mA) High State (ISource = 500 mA) Output Voltage During Initialization Phase p g g VCC = 0 to 1.0 V, ISink = 10 A VCC = 1 0 to 5 0 V ISi k = 100 A 1.0 5.0 V, Sink VCC = 5 0 to 13 V, ISink = 1 0 mA 5.0 V 1.0 Output Voltage Rising Edge Slew-Rate (CL = 1.0 nF, TJ = 25C) Output Voltage Falling Edge Slew-Rate (CL = 1.0 nF, TJ = 25C) ERROR AMPLIFIER SECTION Voltage Feedback Input (VE/A out = 2.5 V) Input Bias Current (VFB = 2.5 V) Open Loop Voltage Gain (VE/A out = 2.0 to 4.0 V) VFB IFB-ib AVOL 2.42 -2.0 65 2.5 -0.6 70 2.58 - - V A dB V VOL VOH VOL - - - dVo/dT dVo/dT - - - 0.1 01 0.1 01 300 -300 1.0 1.0 10 1.0 10 - - V/s V/s - - - - 1.0 1.4 1.5 2.0 1.2 2.0 2.0 2.7 V Symbol Min Typ Max Unit
NOTES: 3. Adjust VCC above the startup threshold before setting to 12 V. 4. Low duty cycle pulse techniques are used during test to maintain junction temperature as close to ambient as possible. 5. VC must be greater than 5.0 V.
2
MOTOROLA ANALOG IC DEVICE DATA
MC44603A
ELECTRICAL CHARACTERISTICS (continued) (VCC and VC = 12 V, [Note 3], Rref = 10 k, CT = 820 pF, for typical values TA = 25C, for min/max values TA = -25 to +85C [Note 4], unless otherwise noted.)
Characteristic ERROR AMPLIFIER SECTION (continued) Unity Gain Bandwidth TJ = 25C TJ = -25 to +85C Voltage Feedback Input Line Regulation (VCC = 10 to 15 V) Output Current Sink (VE/A out = 1.5 V, VFB = 2.7 V) TA = -25 to +85C Source (VE/A out = 5.0 V, VFB = 2.3 V) TA = -25 to +85C Output Voltage Swing High State (IE/A out (source) = 0.5 mA, VFB = 2.3 V) Low State (IE/A out (sink) = 0.33 mA, VFB = 2.7 V) REFERENCE SECTION Reference Output Voltage (VCC = 10 to 15 V) Reference Current Range (Iref = Vref/Rref, R = 5.0 k to 25 k) Reference Voltage Over Iref Range OSCILLATOR AND SYNCHRONIZATION SECTION Frequency TA = 0 to +70C TA = -25 to +85C Frequency Change with Voltage (VCC = 10 to 15 V) Frequency Change with Temperature (TA = -25 to +85C) Oscillator Voltage Swing (Peak-to-Peak) Ratio Charge Current/Reference Current TA = 0 to +70C (VCT = 2.0 V) TA = -25 to +85C Fixed Maximum Duty Cycle = Idischarge/(Idischarge + Icharge) Ratio Standby Discharge Current versus IR F Stby (Note 6) TA = 0 to +70C TA = -25 to +85C (Note 8) VR F Stby (IR F Stby = 100 A) Frequency in Standby Mode (RF Stby (Pin 15) = 25 k) Current Range Synchronization Input Threshold Voltage (Note 7) Synchronization Input Current Minimum Synchronization Pulse Width (Note 8) UNDERVOLTAGE LOCKOUT SECTION Startup Threshold Output Disable Voltage After Threshold Turn-On (UVLO 1) TA = 0 to +70C TA = -25 to +85C Reference Disable Voltage After Threshold Turn-On (UVLO 2) Vstup-th Vdisable1 8.6 8.3 Vdisable2 7.0 9.0 - 7.5 9.4 9.6 8.0 V 13.6 14.5 15.4 V V fOSC 44.5 44 fOSC/V fOSC/T VOSC(pp) Icharge/Iref 0.375 0.37 D Idisch-Stby/ IR F Stby VR F Stby FStby IR F Stby VinthH VinthL ISync-in tSync 78 0.46 0.43 2.4 18 -200 3.2 0.45 -5.0 - 0.4 - 80 0.53 - 2.5 21 - 3.7 0.7 - - 0.425 0.43 82 0.6 0.63 2.6 24 -50 4.3 0.9 0 0.5 V kHz A V A s % - - - 1.65 48 - 0.05 0.05 1.8 51.5 52 - - 1.95 %/V %/C V - kHz Vref Iref Vref 2.4 -500 -40 2.5 - - 2.6 -100 40 V A mV BW - - VFBline-reg ISink ISource -10 2.0 -2.0 4.0 - - 12 - - 5.5 10 - -0.2 V VOH VOL 5.5 - 6.5 1.0 7.5 1.1 mV mA MHz Symbol Min Typ Max Unit
NOTES: 13. Adjust VCC above the startup threshold before setting to 12 V. 14. Low duty cycle pulse techniques are used during test to maintain junction temperature as close to ambient as possible. 16. Standby is disabled for VR P Stby < 25 mV typical. 17. If not used, Synchronization input must be connected to Ground. 18. Synchronization Pulse Width must be shorter than tOSC = 1/fOSC.
MOTOROLA ANALOG IC DEVICE DATA
3
MC44603A
ELECTRICAL CHARACTERISTICS (continued) (VCC and VC = 12 V, [Note 3], Rref = 10 k, CT = 820 pF, for typical values TA = 25C,
for min/max values TA = -25 to +85C [Note 4], unless otherwise noted.) Characteristic DEMAGNETIZATION DETECTION SECTION (Note 9) Demagnetization Detect Input Demagnetization Comparator Threshold (VPin 9 Decreasing) Propagation Delay (Input to Output, Low to High) Input Bias Current (Vdemag = 65 mV) Negative Clamp Level (Idemag = -2.0 mA) Positive Clamp Level (Idemag = 2.0 mA) SOFT-START SECTION (Note 11) Ratio Charge Current/Iref TA = 0 to +70C TA = -25 to +85C Discharge Current (Vsoft-start = 1.0 V) Clamp Level Duty Cycle (Rsoft-start = 12 k) Duty Cycle (Vsoft-start (Pin 11) = 0.1 V) OVERVOLTAGE SECTION Protection Threshold Level on VOVP Propagation Delay (VOVP > 2.58 V to Vout Low) Protection Level on VCC TA = 0 to +70C TA = -25 to +85C Input Resistance TA = 0 to +70C TA = -25 to +85C FOLDBACK SECTION (Note 10) Current Sense Voltage Threshold (Vfoldback (Pin 5) = 0.9 V) Foldback Input Bias Current (Vfoldback (Pin 5) = 0 V) STANDBY SECTION Ratio IR P Stby/Iref TA = 0 to +70C TA = -25 to +85C Ratio Hysteresis (Vh Required to Return to Normal Operation from Standby Operation) TA = 0 to +70C TA = -25 to +85C Current Sense Voltage Threshold (VR P Stby (Pin 12) = 1.0 V) CURRENT SENSE SECTION Maximum Current Sense Input Threshold (Vfeedback (Pin 14) = 2.3 V and Vfoldback (Pin 6) = 1.2 V) Input Bias Current Propagation Delay (Current Sense Input to Output at VTH of MOS transistor = 3.0 V) TOTAL DEVICE Power Supply Current Startup (VCC = 13 V with VCC Increasing) Operating TA = -25 to +85C (Note 3) Power Supply Zener Voltage (ICC = 25 mA) Thermal Shutdown ICC - 13 VZ - 18.5 - 0.3 17 - 155 0.45 20 - - V C mA VCS-th ICS-ib - 0.96 -10 - 1.0 -2.0 120 1.04 - 200 V A ns IR P Stby/Iref 0.37 0.36 Vh/VR P Stby 1.42 1.4 VCS-Stby 0.28 1.5 - 0.31 1.58 1.6 0.34 V 0.4 - 0.43 0.44 - - VCS-th Ifoldback-lb 0.86 -6.0 0.89 -2.0 0.9 - V A VCC prot 16.1 15.9 - 1.5 1.4 2.0 - 3.0 3.4 17 - 17.9 18.1 k VOVP-th 2.42 1.0 2.5 - 2.58 3.0 V s V Iss(ch)/Iref 0.37 0.36 Idischarge Vss(CL) Dsoft-start 12k Dsoft-start 1.5 2.2 36 - 0.4 - 5.0 2.4 42 - 0.43 0.44 - 2.6 49 0 mA V % - Vdemag-th - Idemag-lb CL(neg) CL(pos) 50 - -0.5 - - 65 0.25 - -0.38 0.72 80 - - - - mV s A V V Symbol Min Typ Max Unit
NOTES: 13. Adjust VCC above the startup threshold before setting to 12 V. 14. Low duty cycle pulse techniques are used during test to maintain junction temperature as close to ambient as possible. 19. This function can be inhibited by connecting Pin 8 to Gnd. This allows a continuous current mode operation. 10. This function can be inhibited by connecting Pin 5 to VCC. 11. The MC44603A can be shut down by connecting the Soft-Start pin (Pin 11) to Ground.
4
MOTOROLA ANALOG IC DEVICE DATA
MC44603A
Representative Block Diagram
RF Stby Rref
RF Stby 15 16 Vref Negative Active Clamp Demag Detect 8 Sync Input 9 0.4 Iref 1.0 V R 1.6 V CT 10 CT R Q + 3.6 V S VOSC S Q R 0.4 Iref Vref Vref 0.4 Iref RPwr Stby 12 Feed- back 14 Compen- sation 13 5 Foldback Input + 2.5 V VCC 1.0 mA 2R Error Amplifier 0.6 Iref 0.8 Iref Vref IDischarge Vref Vref 0.25 IF Stby 0.2 Iref Thermal Shutdown Vref 0.4 Iref 2.0 s Delay Vref 5.0 s Delay 11.6 k OVP 2.0 k IDischarge/2 Current Mirror X2 + 1.6 V + 2.5 V Current Sense Input 7 R 1.0 V 2.4 V 5.0 mA UVLO1 VCC + 9.0 V 6 ROVP VOVP Out Vref VCC Output 3 4 Gnd Q S VC 2 R Q S UVLO2
VCC + 65 mV + 3.7 V VDemag Out Synchro VOSC prot Vref + Reference Block Iref IF Stby VCC 14.5 V/7.5 V 18.0 V 1
Vaux
Vref
+ 0.7 V
To Power Transformer
11 SS/Dmax/VM = Sink only = Positive True Logic RSS CSS
This device contains 243 active transistors.
MOTOROLA ANALOG IC DEVICE DATA
5
MC44603A
Figure 1. Timing Resistor versus Oscillator Frequency
100 Rref , TIMING RESISTANCE (k ) CT = 100 pF CT = 500 pF 10000 C T, TIMING CAPACITOR (pF) VCC = 16 V TA = 25C VCC = 16 V TA = 25C Rref = 10 k RF Stby = 2.0 k RF Stby = 5.0 k RF Stby = 27 k RF Stby = 100 k 100 k fOSC, Oscillator Frequency (Hz) 1.0 M 300 10 k 100 k fOSC, Oscillator Frequency (Hz) 1.0 M
Figure 2. Standby Mode Timing Capacitor versus Oscillator Frequency
CT = 1000 pF 10
1000
CT = 2200 pF 3.0 10 k
Figure 3. Oscillator Frequency versus Temperature
51 50 49 48 47 46 45 44 -50 -25 0 25 50 VCC = 12 V Rref = 10 k CT = 820 pF 75 100 Icharge/Iref = RATIO CHARGE CURRENT/ REFERENCE CURRENT f OSC, OSCILLATOR FREQUENCY (kHz) 52 0.43 0.42 0.41 0.40 0.39 0.38 0.37 -50
Figure 4. Ratio Charge Current/Reference Current versus Temperature
VCC = 12 V Rref = 10 k CT = 820 pF -25 0 25 50 75 100
TA, AMBIENT TEMPERATURE (C)
TA, AMBIENT TEMPERATURE (C)
Figure 5. Output Waveform
600 I O , OUTPUT CURRENT (mA) 400 200 0 -200 -400 Voltage -600 -800 -1000 1.0 s/Div 10 0 Current VCC = 12 V CL = 2200 pF TA = 25C 70 VO , OUTPUT DRIVE VOLTAGE (V) 60 50 40 30 20 VO , OUTPUT DRIVE VOLTAGE (V) 70 60 50 40 30 20 10 0 ICC VO
Figure 6. Output Cross Conduction
300 VCC = 12 V CL = 2200 pF TA = 25C Current 200 100 0 -100 -200 Voltage -300 -400 -500 1.0 s/Div
-10
-10
6
MOTOROLA ANALOG IC DEVICE DATA
MC44603A
VOH , SOURCE OUTPUT SATURATION VOLTAGE (V)
Figure 7. Oscillator Discharge Current versus Temperature
500 Idisch , DISCHARGE CURRENT (A) 475 450 425 400 375 350 325 300 -50 -25 0 25 50 VCC = 12 V Rref = 10 k CT = 820 pF 75 100
Figure 8. Source Output Saturation Voltage versus Load Current
2.5
2.0
1.5 VCC = 12 V Rref = 10 k CT = 820 pF TA = 25C 0 100 200 300 400 500
1.0
TA, AMBIENT TEMPERATURE (C)
Isource, OUTPUT SOURCE CURRENT (mA)
VOL , SINK OUTPUT SATURATION VOLTAGE (V)
Figure 9. Sink Output Saturation Voltage versus Sink Current
2.0 1.6 1.2 0.8 0.4 0 0 TA = 25C VCC = 12 V 80 s Pulsed Load 120 Hz Rate 100 200 300 400 500 Sink Saturation (Load to VCC) GAIN (dB) 80 60 40 20 0 -20 Isink, SINK OUTPUT CURRENT (mA)
Figure 10. Error Amplifier Gain and Phase versus Frequency
VCC = 12 V G = 10 Vin = 30 mV VO = 2.0 to 4.0 V RL = 100 k TA = 25C
140 PHASE (DEGREES)
50
100
101
10 2 f, FREQUENCY (kHz)
103
-40 104
2.60 VFB, VOLTAGE FEEDBACK INPUT (V) VCC = 12 V G = 10 VO = 2.0 to 4.0 V RL = 100 k
Vdemag-th, DEMAG COMPARATOR THRESHOLD (mV)
Figure 11. Voltage Feedback Input versus Temperature
Figure 12. Demag Comparator Threshold versus Temperature
80 75 70 65 60 55 50 -50 VCC = 12 V
2.55
2.50
2.45
2.40 -50
-25
0
25
50
75
100
-25
0
25
50
75
100
TA, AMBIENT TEMPERATURE (C)
TA, AMBIENT TEMPERATURE (C)
MOTOROLA ANALOG IC DEVICE DATA
7
MC44603A
Figure 13. Current Sense Gain versus Temperature
3.2 A VCS, CURRENT SENSE GAIN R JA , THERMAL RESISTANCE JUNCTION-TO-AIR ( C/W)
Figure 14. Thermal Resistance and Maximum Power Dissipation versus P.C.B. Copper Length
Printed circuit board heatsink example
3.1
80 60 40 20 0 0 10 RJA
L
2.0 oz Copper
4.0 3.0 2.0
L 3.0 mm Graphs represent symmetrical layout
3.0
2.9
VCC = 12 V Rref = 10 k CT = 820 pF -25 0 25 50 75 100
PD(max) for TA = 70C
1.0 0 50
2.8 -50
TA, AMBIENT TEMPERATURE (C)
20 30 L, LENGTH OF COPPER (mm)
40
Figure 15. Propagation Delay Current Sense Input to Output versus Temperature
140 PROPAGATION DELAY (ns) 0.35 0.30 STARTUP CURRENT (mA) 120 0.25 0.20 0.15 0.10 0.05 0 -25 0 25 50 75 100 0
Figure 16. Startup Current versus VCC
100 VCC = 12 V Rref = 10 k CT = 820 pF 80 -50
Rref = 10 k CT = 820 pF
2.0
4.0
6.0
8.0
10
12
14
TA, AMBIENT TEMPERATURE (C)
VCC, SUPPLY VOLTAGE (V)
Figure 17. Supply Current versus Supply Voltage
16 ICC , SUPPLY CURRENT (mA) 14 12 10 8.0 6.0 4.0 2.0 0 2.0 TA = 25C Rref = 10 k CT = 820 pF VFB = 0 V VCS = 0 V 4.0 6.0 8.0 10 12 14 16 VZ, ZENER VOLTAGE (V) 21.0 20.5 20.0 19.5 19.0 -50 21.5
Figure 18. Power Supply Zener Voltage versus Temperature
ICC = 25 mA
-25
0
25
50
75
100
VCC, SUPPLY VOLTAGE (V)
TA, AMBIENT TEMPERATURE (C)
8
MOTOROLA ANALOG IC DEVICE DATA
P D, MAXIMUM POWER DISSIPATION (W)
100
5.0
EEEEE EEEEE
MC44603A
Figure 19. Startup Threshold Voltage versus Temperature
15.5 9.50
Vstup-th , STARTUP THRESHOLD VOLTAGE (V)
Figure 20. Disable Voltage After Threshold Turn-On (UVLO1) versus Temperature
14.5 VCC Increasing 14.0
Vdisable1 , UVLO1 (V)
15.0
9.25
9.00 VCC Decreasing 8.55
13.5 -50
-25
0
25
50
75
100
8.50 -50
-25
0
25
50
75
100
TA, AMBIENT TEMPERATURE (C)
TA, AMBIENT TEMPERATURE (C)
8.0 7.8 Vdisable2 , UVLO2 (V) 7.6 7.4 VCC Decreasing 7.2 7.0 6.8 -50
VOVP-th, PROTECTION THRESHOLD LEVEL (V)
Figure 21. Disable Voltage After Threshold Turn-On (UVLO2) versus Temperature
Figure 22. Protection Threshold Level on VOVP versus Temperature
2.60 2.55 2.50 2.45 2.40 2.35 2.30 -50 VCC = 12 V
-25
0
25
50
75
100
-25
0
25
50
75
100
TA, AMBIENT TEMPERATURE (C)
TA, AMBIENT TEMPERATURE (C)
Figure 23. Protection Level on VCC versus Temperature
18 VCC prot , PROTECTION LEVEL (V) PROPAGATION DELAY (s) Rref = 10 k CT = 820 pF Pin 6 Open 3.0
Figure 24. Propagation Delay (VOVP > 2.58 V to Vout Low) versus Temperature
17.5
2.5
17
2.0
16.5
1.5
VCC = 12 V Rref = 10 k CT = 820 pF -25 0 25 50 75 100
16 -50
-25
0
25
50
75
100
1.0 -50
TA, AMBIENT TEMPERATURE (C)
TA, AMBIENT TEMPERATURE (C)
MOTOROLA ANALOG IC DEVICE DATA
9
MC44603A
I R P Stby , STANDBY REFERENCE CURRENT (A)
Figure 25. Standby Reference Current versus Temperature
265 260 255 250 245 240 235 230 -50 -25 0 25 50 75 100 VR P Stdby (Pin 12) Voltage Increasing VCS-stby , CURRENT SENSE THRESHOLD STANDBY MODE (V) 270 0.33
Figure 26. Current Sense Voltage Threshold Standby Mode versus Temperature
0.32
0.31
VCC = 12 V Rref = 10 k CT = 820 pF Pin 12 Clamped at 1.0 V -25 0 25 50 75 100
0.30 -50
TA, AMBIENT TEMPERATURE (C)
TA, AMBIENT TEMPERATURE (C)
PIN FUNCTION DESCRIPTION
Pin 1 2 3 4 5 VCC VC Output Gnd Foldback Input Name Description This pin is the positive supply of the IC. The operating voltage range after startup is 9.0 to 14.5 V. The output high state (VOH) is set by the voltage applied to this pin. With a separate connection to the power source, it can reduce the effects of switching noise on the control circuitry. Peak currents up to 750 mA can be sourced or sunk, suitable for driving either MOSFET or Bipolar transistors. This output pin must be shunted by a Schottky diode, 1N5819 or equivalent. The ground pin is a single return, typically connected back to the power source; it is used as control and power ground. The foldback function provides overload protection. Feeding the foldback input with a portion of the VCC voltage (1.0 V max) establishes on the system control loop a foldback characteristic allowing a smoother startup and sharper overload protection. Above 1.0 V the foldback input is inactive. When the overvoltage protection pin receives a voltage greater than 17 V, the device is disabled and requires a complete restart sequence. The overvoltage level is programmable. A voltage proportional to the current flowing into the power switch is connected to this input. The PWM latch uses this information to terminate the conduction of the output buffer when working in a current mode of operation. A maximum level of 1.0 V allows either current or voltage mode operation. A voltage delivered by an auxiliary transformer winding provides to the demagnetization pin an indication of the magnetization state of the flyback transformer. A zero voltage detection corresponds to complete core saturation. The demagnetization detection ensures a discontinuous mode of operation. This function can be inhibited by connecting Pin 8 to Gnd. The synchronization input pin can be activated with either a negative pulse going from a level between 0.7 V and 3.7 V to Gnd or a positive pulse going from a level between 0.7 V and 3.7 V up to a level higher than 3.7 V. The oscillator runs free when Pin 9 is connected to Gnd. The normal mode oscillator frequency is programmed by the capacitor CT choice together with the Rref resistance value. CT, connected between Pin 10 and Gnd, generates the oscillator sawtooth. A capacitor, resistor or a voltage source connected to this pin limits the switching duty-cycle. This pin can be used as a voltage mode control input. By connecting Pin 11 to Ground, the MC44603A can be shut down. A voltage level applied to the RP Standby pin determines the output power level at which the oscillator will turn into the reduced frequency mode of operation (i.e. standby mode). An internal hysteresis comparator allows to return in the normal mode at a higher output power level. The error amplifier output is made available for loop compensation. This is the inverting input of the Error Amplifier. It can be connected to the switching power supply output through an optical (or other) feedback loop. The reduced frequency or standby frequency programming is made by the RF Standby resistance choice. Rref sets the internal reference current. The internal reference current ranges from 100 A to 500 A. This requires that 5.0 k Rref 25 k.
6 7
Overvoltage Protection Current Sense Input Demagnetization Detection
8
9
Synchronization Input CT Soft-Start/Dmax/ Voltage-Mode RP Standby
10 11
12
13 14 15 16
E/A Out Voltage Feedback RF Standby Rref
10
MOTOROLA ANALOG IC DEVICE DATA
MC44603A
Figure 27. Starting Behavior and Overvoltage Management
No-Take Over VCC VCC prot Vstup-th Vdisable1 Vdisable2 Startup Restart Loop Failure >2.0 s
Normal Mode
Vref
UVLO1
VPin 11 (Soft-Start)
VOVP Out
Output
ICC 17 mA 0.3 mA
VDemag In
Output (Pin 3)
VDemag Out
VDemag In
MOTOROLA ANALOG IC DEVICE DATA
III IIIIIIII II III IIIIIIII II III IIIIIIII II
Figure 28. Demagnetization
Demagnetization Management VDemag Out Oscillator Buffer Output
11
MC44603A
Figure 29. Switching Off Behavior
VCC Vstup-th Vdisable1 Vdisable2
Vref
UVLO1
VPin 11 (Soft-Start)
ICC 17 mA 0.3 mA
Figure 30. Oscillator
VCT 1.0 V VStby 3.6 V 1.6 V
VDemag Out
VOSC
VOSC prot
VDemag Out
Synchronization Input
Oscillator
CT VStby
12
III III
VOSC prot VOSC
Output (Pin 3)
MOTOROLA ANALOG IC DEVICE DATA
MC44603A
Figure 31. Soft-Start & Dmax
Vref
VCSS + 1.6 V VCT 3.6 V VCT low 1.6 V
Soft-Start
Internal Clamp
External Clamp
VOSC
Output (Pin 3)
OPERATING DESCRIPTION
Error Amplifier A fully compensated Error Amplifier with access to the inverting input and output is provided. It features a typical dc voltage gain of 70 dB. The noninverting input is internally biased at 2.5 V and is not pinned out. The converter output voltage is typically divided down and monitored by the inverting input. The maximum input bias current with the inverting input at 2.5 V is -2.0 A. This can cause an output voltage error that is equal to the product of the input bias current and the equivalent input divider source resistance. The Error Amp output (Pin 13) is provided for external loop compensation. The output voltage is offset by two diode drops ( 1.4 V) and divided by three before it connects to the inverting input of the Current Sense Comparator. This guarantees that no drive pulses appear at the Output (Pin 3) when Pin 13 is at its lowest state (VOL). The Error Amp minimum feedback resistance is limited by the amplifier's minimum source current (0.2 mA) and the required output voltage (VOH) to reach the current sense comparator's 1.0 V clamp level: Rf(min) Figure 32. Error Amplifier Compensation
+ Compensation RFB Cf 13 Rf 14 2.5 V Error Amplifier 1.0 mA
2R R Current Sense Comparator 1.0 V Gnd 4
Voltage Feedback Input 5 Foldback Input R1 R2 From Power Supply Output
) [ 3.0 (1.0 V)mA 1.4 V + 22 kW 0.2
Current Sense Comparator and PWM Latch The MC44603A can operate as a current mode controller or as a voltage mode controller. In current mode operation, the MC44603A uses the current sense comparator. The output switch conduction is initiated by the oscillator and terminated when the peak inductor current reaches the
MOTOROLA ANALOG IC DEVICE DATA
13
MC44603A
threshold level established by the Error Amplifier output (Pin 13). Thus, the error signal controls the peak inductor current on a cycle-by-cycle basis. The Current Sense Comparator PWM Latch ensures that only a single pulse appears at the Source Output during the appropriate oscillator cycle. The inductor current is converted to a voltage by inserting the ground referenced sense resistor RS in series with the power switch Q1. This voltage is monitored by the Current Sense Input (Pin 7) and compared to a level derived from the Error Amp output. The peak inductor current under normal operating conditions is controlled by the voltage at Pin 13 where: V(Pin 13) - 1.4 V Ipk 3 RS The Current Sense Comparator threshold is internally clamped to 1.0 V. Therefore, the maximum peak switch current is: 1.0 V Ipk(max) RS Figure 34. Oscillator
Vref 0.4 Iref CVOS prot 1.0 V COSC Low VOSC prot VOSC 1.6 V 10 CT CT < 1.6 V Discharge RQ COSC High Disch S COSC Regul 0 1 0 IRegul IDischarge 1 RQ LOSC S Synchro VDemag Out
3.6 V
[
[
Figure 33. Output Totem Pole
Vin VC UVLO VOSC prot R2 VDemag Out Thermal Protection S RQ R PWM Latch Current Sense Comparator 3 D 1N5819 Current Substrate Sense 7 C R3 CT 10 Q1 14
Figure 35. Simplified Block Oscillator
Vref
ICharge 0.4 Iref 0 1
COSC Regul 1.6 V 0: Discharge Phase 1: Charge Phase IRegul
IDischarge R RS
Series gate resistor, R2, will dampen any high frequency oscillations caused by the MOSFET input capacitance and any series wiring inductance in the gate-source circuit. Diode D is required if the negative current into the output drive pin exceeds 15 mA.
Oscillator The oscillator is a very accurate sawtooth generator that can work either in free mode or in synchronization mode. In this second mode, the oscillator stops in the low state and waits for a demagnetization or a synchronization pulse to start a new charging cycle. * The Sawtooth Generation: In the steady state, the oscillator voltage varies between about 1.6 V and 3.6 V. The sawtooth is obtained by charging and discharging an external capacitor CT (Pin 10), using two distinct current sources = Icharge and Idischarge. In fact, CT is permanently connected to the charging current source (0.4 Iref) and so, the discharge current source has to be higher than the charge current to be able to decrease the CT voltage (refer to Figure 35). This condition is performed, its value being (2.0 Iref) in normal working and (0.4 Iref + 0.5 IF Stby in standby mode).
Two comparators are used to generate the sawtooth. They compare the CT voltage to the oscillator valley (1.6 V) and peak reference (3.6 V) values. A latch (Ldisch) memorizes the oscillator state. In addition to the charge and discharge cycles, a third state can exist. This phase can be produced when, at the end of the discharge phase, the oscillator has to wait for a synchronization or demagnetization pulse before restarting. During this delay, the CT voltage must remain equal to the oscillator valley value (]1.6 V). So, a third regulated current source IRegul controlled by COSC Regul, is connected to CT in order to perfectly compensate the (0.4 Iref) current source that permanently supplies CT. The maximum duty cycle is 80%. Indeed, the on-time is allowed only during the oscillator capacitor charge. Consequently: Tcharge = CT x V/Icharge Tdischarge = CT x V/Idischarge where: Tcharge is the oscillator charge time V is the oscillator peak-to-peak value Icharge is the oscillator charge current and Tdischarge is the oscillator discharge time Idischarge is the oscillator discharge current
14
MOTOROLA ANALOG IC DEVICE DATA
MC44603A
So, as fS = 1 /(Tcharge + Tdischarge) when the Regul arrangement is not activated, the operating frequency can be obtained from the graph in Figure 1. NOTE: The output is disabled by the signal VOSC prot when VCT is lower than 1.0 V (refer to Figure 30). Synchronization and Demagnetization Blocks To enable the output, the LOSC latch complementary output must be low. Reset is activated by the Ldisch output during the discharge phase. To restart, the LOSC has to be set (refer to Figure 34). To perform this, the demagnetization signal and the synchronization must be low. * Synchronization: The synchronization block consists of two comparators that compare the synchronization signal (external) to 0.7 and 3.7 V (typical values). The comparators' outputs are connected to the input of an AND gate so that the final output of the block should be : - high when 0.7 < SYNC < 3.7 V - low in the other cases. As a low level is necessary to enable the output, synchronized low level pulses have to be generated on the output of the synchronization block. If synchronization is not required, the Pin 9 must be connected to the ground. Figure 36. Synchronization
3.7 V C Dem Oscillator Sync 9 Output Buffer 0.7 V 65 mV D
A diode D has been incorporated to clamp the positive applied voltages while an active clamping system limits the negative voltages to typically -0.33 V. This negative clamp level is sufficient to avoid the substrate diode switching on. In addition to the comparator, a latch system has been incorporated in order to keep the demagnetization block output level low as soon as a voltage lower than 65 mV is detected and as long as a new restart is produced (high level on the output) (refer to Figure 38). This process prevents ringing on the signal at Pin 8 from disrupting the demagnetization detection. This results in a very accurate demagnetization detection. The demagnetization block output is also directly connected to the output, disabling it during the demagnetization phase (refer to Figure 33). NOTE: The demagnetization detection can be inhibited by connecting Pin 8 to the ground. Figure 38. Demagnetization Block
Oscillator Buffer Output RQ Demag S VCC VDemag Out Negative Active Clamping System 8
Standby * Power Losses in a Classical Flyback Structure Figure 39. Power Losses in a Classical Flyback Structure
Vin + Rstartup VCC MC44603A RS Snubber 0.75 V Clamping Network
* Demagnetization: In flyback applications, a good means to detect magnetic saturation of the transformer core, or demagnetization, consists in using the auxiliary winding voltage. This voltage is: - negative during the on-time, - positive during the off-time, - equal to zero for the dead-time with generally some - ringing (refer to Figure 37). That is why, the MC44603A demagnetization detection consists of a comparator that can compare the auxiliary winding voltage to a reference that is typically equal to 65 mV. Figure 37. Demagnetization Detection
RICL AC Line
+
VPin 8
Zero Current Detection
In a classical flyback (as depicted in Figure 39), the standby losses mainly consist of the energy waste due to: - the startup resistor Rstartup - the consumption of the IC and - the power switch control - the inrush current limitation resistor RICL - the switching losses in the power switch - the snubber and clamping network Pstartup is nearly constant and is equal to: (Vin-VCC)2 Rstartup Pstartup Pcontrol PICL PSW PSN-CLN
65 mV
-0.33 V On-Time Off-Time Dead-Time
MOTOROLA ANALOG IC DEVICE DATA
15
MC44603A
PICL only depends on the current drawn from the mains. Losses can be considered constant. This waste of energy decreases when the standby losses are reduced. Pcontrol increases when the oscillator frequency is increased (each switching requires some energy to turn on the power switch). PSW and PSN-CLN are proportional to the switching frequency. Consequently, standby losses can be minimized by decreasing the switching frequency as much as possible. The MC44603A was designed to operate at a standby frequency lower than the normal working one. * Standby Power Calculations with MC44603A During a switching period, the energy drawn by the transformer during the on-time to be transferred to the output during the off-time, is equal to: 1 xLxI 2 E pk 2 where: The V CS threshold level is typically equal to [(VR P Stby)/3] and if the corresponding power threshold is labelled PthL: VR P Stby 2 PthL 0.5 x L x x fS 3.0 RS
+
And as:
VR P Stby
+ RP Stby x 0.4 x Iref V + RR P Stby x 0.4 x Rref ref
x PthL L x fS
RP Stby
RS + 10.6 x Vref x Rref
+
- L is the transformer primary inductor, - lpk is the inductor peak current. Input power is labelled Pin: Pin Also, Ipk
+ 0.5 x L x Ipk2 x fS + VRCS S
Thus, when the power drawn by the converter decreases, VCS decreases and when VCS becomes lower than [VCS-th x (VR P Stby)/3], the standby mode is activated. This results in an oscillator discharge current reduction in order to increase the oscillator period and to diminish the switching frequency. As it is represented in Figure 40, the (0.8 x Iref) current source is disconnected and is replaced by a lower value one (0.25 x IF Stby). Where: IF Stby = Vref/RF Stby In order to prevent undesired mode switching when power is close to the threshold value, a hysteresis that is proportional to VR P Stby is incorporated creating a second VCS threshold level that is equal to [2.5 x (VR P Stby)/3]. When the standby comparator output is high, a second current source (0.6 x Iref) is connected to Pin 12. Finally, the standby mode function can be shown graphically in Figure 41. Figure 41. Dynamic Mode Change
Pin fS
where fS is the normal working switching frequency.
where RS is the resistor used to measure the power switch current. Thus, the input power is proportional to VCS2 (VCS being the internal current sense comparator input). That is why the standby detection is performed by creating a VCS threshold. An internal current source (0.4 x Iref) sets the threshold level by connecting a resistor to Pin 12. As depicted in Figure 40, the standby comparator noninverting input voltage is typically equal to (3.0 x VCS + VF) while the inverter input value is (VR P Stby + VF). Figure 40. Standby
Vref Vref 0.4 Iref RP Stby 12 0 0.6 Iref 1 CStby 1 Vref Vref 0.8 Iref Oscillator Discharge Current
Normal Working PthH PthL [(VR P Stby)/3] Standby
fStby
Vref 0.25 IF Stby 0.2 Iref 0
VCS
2.5 x [(VR P Stby)/3] 1
13 ERAmpOut 2R 1R
IDischarge/2 C. S. Comparator
IDischarge
This curve shows that there are two power threshold levels: - the low one: PthL fixed by VR P Stby - the high one:
Current Mirror X2
+ (2.5)2 x PthL x fStby fS fStby PthH + 6.25 x PthL x fS
PthH
16
MOTOROLA ANALOG IC DEVICE DATA
MC44603A
Maximum Duty Cycle and Soft-Start Control Maximum duty cycle can be limited to values less than 80% by utilizing the Dmax and soft-start control. As depicted in Figure 42, the Pin 11 voltage is compared to the oscillator sawtooth. Figure 42. Dmax and Soft-Start
Vref 0.4 Iref 11 DZ Soft-Start Capacitor 2.4 V CDmax VOSC Oscillator Dmax Output Drive Output Control VCC Vdisable2
Figure 45. Foldback Characteristic
Vout VO Nominal New Startup Sequence Initiated Ipk max
Iout Overload
NOTE: Foldback is disabled by connecting Pin 5 to VCC. Overvoltage Protection The overvoltage arrangement consists of a comparator that compares the Pin 6 voltage to Vref (2.5 V) (refer to Figure 46). If no external component is connected to Pin 6, the comparator noninverting input voltage is nearly equal to: 2.0 kW 11.6 kW 2.0 kW The comparator output is high when: 2.0 kW 11.6 kW 2.0 kW
Figure 43. Maximum Duty Cycle Control
Voltage Pin 11 VCT (Pin 10) Dmax
)
x VCC
Using the internal current source (0.4 Iref), the Pin 11 voltage can easily be set by connecting a resistor to this pin. If a capacitor is connected to Pin 11, the voltage increases from 0 to its maximum value progressively (refer to Figure 44), thereby, implementing a soft-start. The soft-start capacitor is discharged internally when the VCC (Pin 1) voltage drops below 9.0 V. Figure 44. Different Possible Uses of Pin 11
Pin 11 R Connected to Pin 11 I = 0.4 Iref VZ RI C VZ RI = RC C // R
If no external component is connected to Pin 11, an internal zener diode clamps the Pin 11 voltage to a value VZ that is higher than the oscillator peak value, disabling soft-start and maximum duty cycle limitation. Foldback As depicted in Figures 32 and 48, the foldback input (Pin 5) can be used to reduce the maximum VCS value, providing foldback protection. The foldback arrangement is a programmable peak current limitation. If the output load is increased, the required converter peak current becomes higher and VCS increases until it reaches its maximum value (normally, VCS max = 1.0 V). Then, if the output load keeps on increasing, the system is unable to supply enough energy to maintain the output voltages in regulation. Consequently, the decreasing output can be applied to Pin 5, in order to limit the maximum peak current. In this way, the well known foldback characteristic can be obtained (refer to Figure 45).
A delay latch (2.0 s) is incorporated in order to sense overvoltages that last at least 2.0 s. If this condition is achieved, VOVP out, the delay latch output, becomes high. As this level is brought back to the input through an OR gate, VOVP out remains high (disabling the IC output) until Vref is disabled. Consequently, when an overvoltage longer than 2.0 s is detected, the output is disabled until VCC is removed and then re-applied. The VCC is connected after Vref has reached steady state in order to limit the circuit startup consumption. The overvoltage section is enabled 5.0 s after the regulator has started to allow the reference Vref to stabilize. By connecting an external resistor to Pin 6, the threshold VCC level can be changed. Figure 46. Overvoltage Protection
Vref VCC Out T 0 VOVP External Resistor 6 2.5 V Delay In VOVP out
x VCC w 2.5 V ) a VCC w 17 V
5.0 s
11.6 k Enable 2.0 k COVLO 2.5 V (Vref) In Out Delay 2.0 s
(If VOVP out = 1.0, the Output is Disabled)
MOTOROLA ANALOG IC DEVICE DATA
17
MC44603A
Undervoltage Lockout Section Figure 47. VCC Management
RF Stby Vref enable VCC 1 1 1 0 Startup 14.5 V UVLO1 (to Soft-Start) 0 Cstartup Reference Block: Voltage and Current Sources Generator (Vref, Iref, ...) Pin 15 Rref Pin 16
Vdisable2 7.5 V CUVLO1 Vdisable1 9.0 V
As depicted in Figure 47, an undervoltage lockout has been incorporated to garantee that the IC is fully functional before allowing system operation. This block particularly, produces Vref (Pin 16 voltage) and Iref that is determined by the resistor Rref connected between Pin 16 and the ground: Vref Iref where Vref 2.5 V (typically) Rref Another resistor is connected to the Reference Block: RF Stby that is used to fix the standby frequency. In addition to this, VCC is compared to a second threshold level that is nearly equal to 9.0 V (Vdisable1). UVLO1 is generated to reset the maximum duty cycle and soft-start block disabling the output stage as soon as VCC becomes lower than Vdisable1. In this way, the circuit is reset and made ready for the next startup, before the reference block is disabled (refer to Figure 29). Finally, the upper limit for the minimum normal operating voltage is 9.4 V (maximum value of Vdisable1) and so the minimum hysteresis is 4.2 V. ((Vstup-th) min = 13.6 V). The large hysteresis and the low startup current of the MC44603A make it ideally suited for off-line converter applications where efficient bootstrap startup techniques are required.
+
+
18
MOTOROLA ANALOG IC DEVICE DATA
MC44603A
Figure 48. 250 W Input Power Off-Line Flyback Converter with MOSFET Switch
185 Vac to 270 Vac
RFI Filter
R1 1.0/5.0 W C4 ... C7 1.0 nF/1000 V
C3 1.0 nF/1.0 kV
D1 ... D4 1N4007 C1 220 F R20 22 k 5.0 W C17 47 nF
R3 4.7 M
C32 220 pF
L2 22.5 H
150 V/0.6 A
R2 68 k/2.0 W Sync C8 2.2 nF 9 C9 1.0 nF 10 C10 1.0 F 11 MC44603AP 12 13 14 15 16 R17 22 k R18 27 k R19 10 k 6 5 4 *D15 1N5819 3 R10 10 2 R11 39 1 R12 22 C13 100 nF 7 C15 1.0 nF R7 180 k R8 15 k 8 R9 1.0 k C16 100 pF C2 220 F R12 27 k
D5 1N4934
D8 MR856 C30 100 F C29 220 pF
C33 100 F
C31 0.1 F
L1 1.0 H D6 1N4148 C14 4.7 nF
D7 M856
30 V/2.0 A D9 MR852 C27 1000 F C28 0.1 F
R5 1.2 k
Laux
Lp
C26 220 pF R6 150 D10 MR852 MTP6N60E R26 1.0 k C18 2.2 nF D12 MR856 C25 1000 F 14 V/2.0 A C24 0.1 F
R15 5.6 k C11 1.0 nF R15 22 k
C23 220 pF 7.0 V/2.0 A D11 MR852 C21 1000 F R24 270 MOC8101 R21 10 k C19 100 nF R23 147.5 k D14 1N4733 C22 0.1 F
R14 0.2
R13 1.0 k
C20 33 nF R25 1.0 k C12 6.8 nF TL431 R22 2.5 k
* Diode D15 is required if the negative current into the output pin exceeds 15 mA.
MOTOROLA ANALOG IC DEVICE DATA
19
MC44603A
250 W Input Power Fly-Back Converter 185 V - 270 V Mains Range MC44603AP & MTP6N60E
Tests Line Regulation 150 V 130 V 114 V 7.0 V Load Regulation 150 V Cross Regulation Conditions Vin = 185 Vac to 270 Vac Fmains = 50 Hz Iout = 0.6 A Iout = 2.0 A Iout = 2.0 A Iout = 2.0 A Vin = 220 Vac Iout = 0.3 A to 0.6 A Vin = 220 Vac Iout (150 V) = 0.6 A Iout (30 V) = 0 A to 2.0 A Iout (14 V) = 2.0 A Iout (7.0 V) = 2.0 A < 1.0 mV Vin = 220 Vac, Pin = 250 W Vin = 220 Vac, Pout = 0 W 81% 3.3 W 20 kHz fully stable Pout (max) = 270 W Pin = 250 W Safe on all outputs Vac = 160 V Results
10 mV 10 mV 10 mV 20 mV 50 mV
150 V Efficiency Standby Mode P input Switching Frequency Output Short Circuit Startup
20
MOTOROLA ANALOG IC DEVICE DATA
MC44603A
OUTLINE DIMENSIONS
P SUFFIX PLASTIC PACKAGE CASE 648-08 ISSUE R
-A-
16 9
B
1 8
NOTES: 1. DIMENSIONING AND TOLERANCING PER ANSI Y14.5M, 1982. 2. CONTROLLING DIMENSION: INCH. 3. DIMENSION L TO CENTER OF LEADS WHEN FORMED PARALLEL. 4. DIMENSION B DOES NOT INCLUDE MOLD FLASH. 5. ROUNDED CORNERS OPTIONAL. DIM A B C D F G H J K L M S INCHES MIN MAX 0.740 0.770 0.250 0.270 0.145 0.175 0.015 0.021 0.040 0.70 0.100 BSC 0.050 BSC 0.008 0.015 0.110 0.130 0.295 0.305 0_ 10 _ 0.020 0.040 MILLIMETERS MIN MAX 18.80 19.55 6.35 6.85 3.69 4.44 0.39 0.53 1.02 1.77 2.54 BSC 1.27 BSC 0.21 0.38 2.80 3.30 7.50 7.74 0_ 10 _ 0.51 1.01
F S
C
L
-T- H G D
16 PL
SEATING PLANE
K
J TA
M
M
0.25 (0.010)
M
MOTOROLA ANALOG IC DEVICE DATA
21
MC44603A
OUTLINE DIMENSIONS
DW SUFFIX PLASTIC PACKAGE CASE 751G-02 (SOP-16L) ISSUE A -A-
16 9 NOTES: 1. DIMENSIONING AND TOLERANCING PER ANSI Y14.5M, 1982. 2. CONTROLLING DIMENSION: MILLIMETER. 3. DIMENSIONS A AND B DO NOT INCLUDE MOLD PROTRUSION. 4. MAXIMUM MOLD PROTRUSION 0.15 (0.006) PER SIDE. 5. DIMENSION D DOES NOT INCLUDE DAMBAR PROTRUSION. ALLOWABLE DAMBAR PROTRUSION SHALL BE 0.13 (0.005) TOTAL IN EXCESS OF D DIMENSION AT MAXIMUM MATERIAL CONDITION. MILLIMETERS MIN MAX 10.15 10.45 7.40 7.60 2.35 2.65 0.35 0.49 0.50 0.90 1.27 BSC 0.25 0.32 0.10 0.25 0_ 7_ 10.05 10.55 0.25 0.75 INCHES MIN MAX 0.400 0.411 0.292 0.299 0.093 0.104 0.014 0.019 0.020 0.035 0.050 BSC 0.010 0.012 0.004 0.009 0_ 7_ 0.395 0.415 0.010 0.029
-B-
1 8
8X
P 0.010 (0.25)
M
B
M
16X
D
M
J TA
S
0.010 (0.25)
B
S
F R X 45 _ C -T-
14X
G
K
SEATING PLANE
M
DIM A B C D F G J K M P R
22
MOTOROLA ANALOG IC DEVICE DATA
MC44603A
Motorola reserves the right to make changes without further notice to any products herein. Motorola makes no warranty, representation or guarantee regarding the suitability of its products for any particular purpose, nor does Motorola assume any liability arising out of the application or use of any product or circuit, and specifically disclaims any and all liability, including without limitation consequential or incidental damages. "Typical" parameters which may be provided in Motorola data sheets and/or specifications can and do vary in different applications and actual performance may vary over time. All operating parameters, including "Typicals" must be validated for each customer application by customer's technical experts. Motorola does not convey any license under its patent rights nor the rights of others. Motorola products are not designed, intended, or authorized for use as components in systems intended for surgical implant into the body, or other applications intended to support or sustain life, or for any other application in which the failure of the Motorola product could create a situation where personal injury or death may occur. Should Buyer purchase or use Motorola products for any such unintended or unauthorized application, Buyer shall indemnify and hold Motorola and its officers, employees, subsidiaries, affiliates, and distributors harmless against all claims, costs, damages, and expenses, and reasonable attorney fees arising out of, directly or indirectly, any claim of personal injury or death associated with such unintended or unauthorized use, even if such claim alleges that Motorola was negligent regarding the design or manufacture of the part. Motorola and are registered trademarks of Motorola, Inc. Motorola, Inc. is an Equal Opportunity/Affirmative Action Employer.
MOTOROLA ANALOG IC DEVICE DATA
23
MC44603A
Mfax is a trademark of Motorola, Inc. How to reach us: USA / EUROPE / Locations Not Listed: Motorola Literature Distribution; P.O. Box 5405, Denver, Colorado 80217. 303-675-2140 or 1-800-441-2447 MfaxTM: RMFAX0@email.sps.mot.com - TOUCHTONE 602-244-6609 INTERNET: http://Design-NET.com JAPAN: Nippon Motorola Ltd.; Tatsumi-SPD-JLDC, 6F Seibu-Butsuryu-Center, 3-14-2 Tatsumi Koto-Ku, Tokyo 135, Japan. 81-3-3521-8315 ASIA/PACIFIC: Motorola Semiconductors H.K. Ltd.; 8B Tai Ping Industrial Park, 51 Ting Kok Road, Tai Po, N.T., Hong Kong. 852-26629298
24
MOTOROLA ANALOG IC DEVICE DATA MC44603A/D

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